Analog Tips & Tricks

Are you looking for ways to improve your analog and RF circuitry? Engineer Ed Nisley provides a few tips for getting started. He shows you how easy it is to take your PCB wiring skills to the next level. Who knows, your digital projects just might improve too.

Circuit Cellar has always attracted readers who enjoy building gizmos, both at work and for their own use. My December 2004 column, “Building Boxes,” prompted enough comments and suggestions regarding additional techniques that I decided a follow-up was in order.

Although these tricks are designed to improve your analog and RF circuitry, even your digital projects will benefit, because digital is just analog with the gain cranked way up. You’re sure to find at least one technique that will make your next project work better.

I wire most of my projects on PCBs built in my basement shop, using a process that produces both circuit documentation and reasonably high-quality hardware without too much effort. I’ve come up with some tricks that should help you get good results too.

I use CadSoft’s EAGLE schematic capture and board layout software, which runs on Windows, Linux, and Mac OS X (www.cadsoftusa.com). The free version can handle most of the circuits in this column, and the Standard version is reasonably priced. EAGLE is perfectly stable on my SuSE Linux 9.2 desktop system. The board layout program can produce output files in nearly any format, including the Gerber files used in board production shops. I save the output for each layer as a Postscript file, and then import the files into the GNU Image Manipulation Program (GIMP) image-editing program at 600 dpi.

The top image is the top copper layer from an EAGLE board design. The bare board shows several flaws, but the one on the bottom came out fine. The ruler scales are 0.050″ vertically and 1 mm horizontally. The board has extremely small features!

The top image is the top copper layer from an EAGLE board design. The bare board shows several flaws, but the one on the bottom came out fine. The ruler scales are 0.050″ vertically and 1 mm horizontally. The board has extremely small features!

The top image in Photo 1 shows the copper plane pattern for the charge pump LED power supply I described in my April 2005 column. I panelize them with the GIMP to produce a single image with multiple patterns in a rectangular grid. Because all this happens digitally, there’s no loss of resolution and no smudges. I then print the image through an HP LaserJet 1200 on a sheet of toner-transfer film from either Pulsar (www.pulsar.gs) or Techniks (www.techniks.com). It turns out that toner contains a thermoplastic that both adheres to bare copper and resists the etching chemical solution.

Because most of my boards are extremely small, they don’t fill a complete sheet of the toner-transfer film even after I panelize them. I print a sheet of paper, tape a square of film that’s approximately 1″ larger than the patterns atop them, and then run the paper through the printer again. The adhesive on cheaper tapes tends to melt at laser printer temperatures, so use good tape and monitor your results. Put a single strip on the leading edge of the toner-transfer film to allow the paper and film to shift slightly as they pass through the fuser rollers.

This article first appeared in Circuit Cellar 181. You can read the entire article here.

Ed Nisley is an electrical engineer, author, and long-time Circuit Cellar columnist living in Poughkeepsie, NY. His column “Above the Ground Plane” appears in Circuit Cellar every other month. You can contact him at ed.nisley@pobox. com. Write “Circuit Cellar” in the subject line to avoid spam filters.

Analog Filter Essentials

Analog frequency-selective filters are useful for noise reduction, antialiasing before digitizing a signal, frequency response correction, and more. In this article, Circuit Cellar columnist Robert Lacoste explains the differences between filters and how to design them with computer-aided tools.
 

The following article by Robert Lacoste appears in Circuit Cellar 307, 2016.

 
 
Welcome back to the Darker Side. I spoke about operational amplifiers (op-amps) in my last few columns. Op-amps shine in plenty of applications—in particular, to build active filters. This month, I’ll focus on filters—more precisely, analog frequency-selective filters, which are used in audio devices, as well as for noise reduction, antialiasing before digitizing a signal, separation of frequency-multiplexed signals, frequency response correction, and so on.

So analog filters must be in the bag of tricks of any designer. Unfortunately, filter design, or even their use, is often perceived as a difficult task close to black magic. This is, well, unfortunate. Filters are definitively useful, simple, and even fun. I bet a textbook about filters full of math would bore you, right? Well, relax. My goal for this article is more pragmatic. I will try to help you to specify a filter, understand the main filter variants, and efficiently use some great computer-aided design tools. I promise, no Laplace transforms or poles or zeros, just electronics.

FILTER SPECIFICATIONS

Let’s start with some vocabulary. By definition, a filter is a circuit that attenuates some signals more than others, depending on their frequency. Figure 1 depicts the most classic filter types. A low-pass filter lets the low frequencies pass through, but attenuates high-frequency signals. It is perfect for removing high-frequency noise on a signal coming from a sensor.

FIGURE 1: Four classic types of frequency filters. Each one attenuates a specific frequency range.

FIGURE 1: Four classic types of frequency filters. Each one attenuates a specific frequency range. Click image to enlarge.

Conversely, a high-pass filter attenuates the low frequencies, and could in particular remove any DC component of a signal. Band-pass filters are a combination of both, and they attenuate all frequencies below or above a given range. For example, any radio frequency receiver is a band-pass filter, providing attenuation of all signals except for frequencies close to its preset frequency. Lastly, a band stop filter, often called a notch filter, does the opposite, and it attenuates a selected range of frequencies. For example, a 50- or 60-Hz notch filter is included in virtually every weight scale to remove EMC perturbations from the surrounding power lines.

Want to specify a filter? Figure 2 illustrates this on a low-pass filter. The first parameter is the filter cut-off frequency, of course. By definition, this is the frequency at which the filter attenuates the power of the signal by 50%. This means that the losses of the filter will be 3 dB at that frequency. Aren’t you fluent with decibels? A decibel is one tenth of a Bel, and a Bel is the base-10 logarithm of the ratio of two powers. Take your calculator and enter 10 × log(0.5), you will get –3.01, which everybody rounds to –3 dB.

FIGURE 2 A filter (low-pass in this case) is specified by its cutoff frequency f3dB, its ripple in the pass-band, and its rejection in the stopband.

FIGURE 2: A filter (low-pass in this case) is specified by its cutoff frequency f3dB, its ripple in the pass-band, and its rejection in the stopband. Click image to enlarge.

But perhaps an attenuation of 3 dB is already too much for your application. The maximum tolerated variation of signal power in the pass-band (here from DC to fPB) is called the ripple of the filter. Lastly, you will very probably want to specify that the filter must provide a given minimum attenuation, called rejection, above some frequency fSB. Of course, these specifications must be established with care. If you decide that you need a filter with 0.01 dB of ripple up to 10 kHz and 100 dB of rejection from 11 kHz upward, you will probably need plenty of time and cash for the design.

RC FILTERS

I propose to start with the most basic designs: RC filters. The basic low-pass filter is built with one series resistor and one capacitor to ground (see Figure 3). The capacitor impedance gets lower when the frequency increases, and the signal power is attenuated. This filter is called a first-order filter, and it provides an attenuation of 6 dB per octave or 20 dB per decade. (. Simply because 23.33 = 10, and 3.33 × 6 = 20.) That means that, above its cut-off frequency, its attenuation is increased by 6 dB each time the frequency is doubled, or by 20 dB each time it is multiplied by 10. I did the simulation for you with Labcenter Electronics Proteus. Figure 3 shows the result. You can do the same with any Spice-based simulator like the free LT-Spice. The attenuation of this RC filter is –20 dB at 100 kHz, and 20 dB more, meaning –40 dB, at 10 × 100 kHz = 1 MHz as expected.

FIGURE 3 A first-order RC filter (top) provides an attenuation of 20 dB/decade (green curve), whereas a second-order filter provides 40 dB/decade (red).

FIGURE 3: A first-order RC filter (top) provides an attenuation of 20 dB/decade (green curve), whereas a second-order filter provides 40 dB/decade (red). Click image to enlarge.

Such a RC filter can be designed for any cutoff frequency. Just select the proper values for R and C. You might wonder how to calculate the values of the R and C. For a single RC cell, it is really easy. The cutoff frequency is 1/(2pRC).

If you want to increase the steepness of the attenuation, you can chain several RCs. For example, I simulated a second-order RC filter, with two RC cells in series (see Figure 3). As expected, the attenuation is now 12 dB (i.e., 2 × 6) per octave, or 40 dB (i.e., 2 × 20) per decade. Nothing magic. The 3-dB cutoff frequency is pushed downward as compared to a single RC cell, simply because at the 3-dB cutoff of each cell the attenuation is now 6 dB. However, you can see in the graph that even if the falloff in high frequencies is two times better, the drop around the cutoff frequency isn’t improved: it is still “soft.” That’s a limitation of cascaded RC cells. I will present you with a better solution.

Maybe a low-pass filter isn’t what you need. If you prefer a high-pass filter, then just exchange capacitors and resistors. A series capacitor and a resistor to ground would make it. Do you want a band-pass? Just put a low-pass cell in series with a high-pass cell with the appropriate cutoff frequencies. For example, a 10-to-50-kHz band-pass can be built with a 10-kHz high pass and a 50-kHz low pass. And for a notch filter? Do the same with the two filters in parallel. With the same example, a 10-to-50-kHz band stop may be implemented with a 10-kHz low pass and 50-kHz high pass in parallel. Easy.

LC FILTERS

For a given filter performance, is it possible to build a passive analog filter with fewer parts than a multicell RC filter and with improved performance? Yes, you can use LC filters. Here the filter is made with capacitors and inductors, as illustrated in Figure 4. How steep can be their attenuation profile? Very easy. It is the same in the case of RC filters. Count the number of capacitors, add the number of inductors, and you’ll get the order or the filter. Then multiply by 6 dB to get the attenuation per octave, or by 20 dB for an attenuation per decade! For example, the first filter simulated in Figure 4 has one inductor and one capacitor. Two parts, so it is a second-order filter, with the same 40 dB/octave attenuation as the dual RC example in Figure 3. The bottom example has three capacitors and two inductors; therefore, its attenuation is 100 dB (i.e., 5 × 5) per decade or 30 dB (i.e., 5 × 6) per octave. I promise. It’s simple!

FIGURE 4: This simulation shows the frequency response of three LC filters, respectively, of order two, three, and five from top to bottom. Their outputs are open-ended, which imply some overshoot.

FIGURE 4: This simulation shows the frequency response of three LC filters, respectively, of order two, three, and five from top to bottom. Their outputs are open-ended, which imply some overshoot. Click image to enlarge.

Well, nearly. Let’s now see the small details. If you refer back to Figure 4, you’ll see that such LC filters have a weird response around their cutoff frequencies. There is an overshoot, which means they have a positive gain at some frequencies. Of course, such passive filters can’t “create energy.” This positive gain is due to the fact that their output is open-circuited so no energy actually flows anywhere. Don’t be confused. This is not an artifact of the simulation. This would be exactly the same on an actual circuit. The amplitude of the overshoot is directly linked to the so-called quality factor of the L and C parts, and in particular their series resistance. If the capacitor and inductors are ideal, then the overshoot will be infinite at the frequency where the L and C oscillate. That’s why I added a small 47-Ω series resistor on the simulations. If you change the value of this series resistor, then the shape of the gain curve changes. I illustrated it in Figure 5 (top graph) which shows a series resistor ranging from 5 to 100 Ω.

FIGURE 5: The top simulation shows the frequency response of an open-ended LC filter with varying serial resistor value. The bottom simulation shows that the overshoot disappears when the filter is connected to a matched load. X varies from 5 to 100 Ω.

FIGURE 5: The top simulation shows the frequency response of an open-ended LC filter with varying serial resistor value. The bottom simulation shows that the overshoot disappears when the filter is connected to a matched load. X varies from 5 to 100 Ω. Click image to enlarge.

How do you avoid such oscillations? Simply connect the filter’s output to a proper load. If you are a regular reader of my columns, you won’t be surprised: this load must provide an impedance matching with the source impedance. Look at the second example in Figure 5. I added a load resistor R3 of the same value as the source resistor R2 (denoted X). I then asked the simulator to show the resulting gain versus frequency graph with different values for these resistors X, ranging from 5 to 100 Ω again. The shapes are varying, but there are no overshoots. Moreover a precise resistor value provides a very clean and flat response, linked of course with the values of the L and C parts. This value, here 50 ohm, is the characteristic impedance of the LC filter.

So LC filters must be calculated to get the required frequency response but also taking into account the impedance of the load. For second order filters, using just one inductor and one capacitor, the calculation are straightforward. The cutoff frequency is f3dB = 1/[2p√(LC)], and the characteristic impedance is Z = √(L/C). If you know the required cutoff frequency and designed impedance, then you can easily calculate L and C from these two formulas.

The calculation is not so straightforward for higher-order filters, especially as the design choices are numerous. More on that below. Our ancestors used the abacus; now we can use web-based design tools. (Refer to the Resources section of this article for some links to free LC filter calculators.) There is even a great design tool from Coilcraft that allows you to directly order the samples of the required inductors with a mouse click. Easy, I promised.

FROM LC TO ACTIVE FILTERS

Using inductors often isn’t pleasant. They can be heavy and large, and they’re always significantly more expensive than capacitors and resistors. Moreover, inductors are often quite far from ideal components. They can have a high series resistance as well as parasitic capacitance, nasty electromagnetic compatibility behavior, and a couple of other issues. How can you keep the performance of an LC filter without using inductors? With an active filter, usually built around our dear friend the op-amp.

There are basically three ways to build an active filter. The first is to simply add an amplifier to the RC filters I’ve already talked about. For example, you can add a voltage follower after an RC cell in order to reduce its output impedance or to provide some gain. You can also wire an op-amp as a differentiator or integrator, which are first-order filters.

The second solution is to build a switched-capacitor filter circuit. (I devoted my Circuit Cellar 277 column to the subject.) So let’s talk about the third option, which is based on so-called gyrators. What is that? A gyrator is a circuit that mimics the behavior of an inductor, using an op-amp and only resistors and capacitors. You will find plenty of literature on the subject. Of course, this is explained in the bible, Paul Horowitz and Winfield Hill’s The Art of Electronics, but Rod Elliott provides a clear presentation on the subject in “Active Filters Using Gyrators – Characteristics, and Examples,” (Elliott Sound Products, 2014).

Look at Figure 6 where I have illustrated the basic concept. The top part of the schematic is a classic second-order LC high-pass filter with matched source and load impedances. I used a 390-nF capacitor and a 1-mH inductor, resulting in a cutoff frequency of 8 kHz and a characteristic impedance of 50 Ω—here roughly matched with source and load 56-Ω resistors.

FIGURE 6 This simulation shows the transformation of an LC high-pass filter (top) into a gyrator-based circuit (middle), which is really close to the common Sallen Key filter (bottom).

FIGURE 6: This simulation shows the transformation of an LC high-pass filter (top) into a gyrator-based circuit (middle), which is really close to the common Sallen Key filter (bottom). Click image to enlarge.

The response curve shows noting surprising with a 40 dB/decade (i.e., 2 × 20) attenuation in the stopband. Its gain is –6 dB in the passband, as the voltage is divided by two due to the source and load resistors. (The power is divided by 22 = 4, giving –6 dB.) Now look at the middle section of the schematic in Figure 6. The circuit is exactly the same, but I replaced the inductor with an op-amp, a capacitor, and two resistors. That’s a gyrator. If you look now at the resulting graph, you will see that its frequency response is exactly the same as the LC version, at least up to 1 MHz where the characteristics of the op-amp start to be limiting.

Now another magic trick. Compare the gyrator-based schematic with the schematic at the bottom of Figure 6. If you move the parts and the wires around, you will see that they are exactly identical, except the output is now directly connected to the op-amp output. Do you recognize the new schematic? It is a Sallen-Key second-order active high-pass filter. I modified the part values to a more reasonable range, but you can see that the output frequency response is still the same. More precisely, it doesn’t suffer from the 6-dB losses as the signal is taken directly at the output of the op-amp. So Sallen-Key filters, gyrator-based filters, and LC filters are more than cousins.

FILTER RESPONSES

If you want to design a single-cell filter, either a first-order RC filter, a second-order LC, or an active filter, then you will not have a lot of design choices. You can select the desired filter type, cutoff frequency, and impedance, but nothing more. However, for higher-order filters, the choices are wider. The filter is made of several cells, and you can tune each cell separately. Therefore, you will have a better attenuation curve thanks to the higher order (remember, 6 dB per octave multiplied by the order of the filter), as well as more control on the shape of the filter.

Nothing prevents you from designing your own filter, tweaking each cell however you want. However, mathematicians have already calculated several “optimal” filters for certain applications. Do you want to have a response curve as flat as possible in the passband? Stephen Butterworth calculated it for you in 1930. It’s now called the Butterworth filter, of course. Do you prefer to attenuate as quickly as possible the stop-band even if it implies a higher level of ripple in the pass-band? Use a Chebyshev filter, derived from the Chebyshev polynomials. More precisely, this is a family of filters based on the acceptable ripple (e.g., 0.5 dB). The so-called elliptic filters are close.

The last common variant, the Bessel filter, is a little more complex. A Bessel filter is not a great option both in terms of flatness and attenuation; however, it has a key advantage in the time domain. Its so-called group delay is nearly flat. That brings us a little too far here, but these characteristics preserve the shape of the filtered signals in the time domain. I will tackle that subject in another article.

Of course, each variant has drawbacks. For the same filter complexity, a higher ripple in the passband must be accepted to get a higher attenuation in the stop-band. Similarly, a better phase flatness implies a worse frequency response. Life is difficult, but you are the designer, so you have the control. Figure 7 shows the characteristic responses of each filter variant.[1] For more information, I strongly encourage you to have a look at the “Analog Filters” chapter in Hank Zumbahlen’s Linear Circuit Design Handbook (Analog Devices, 2008).

FIGURE 7: These plots show the typical frequency and time (step and impluse) response of the three most common filter variants. (Source: Linear Circuit Design Handbook, Analog Devices)

FIGURE 7: These plots show the typical frequency and time (step and impluse) response of the three most common filter variants. Click image to enlarge. (Source: Linear Circuit Design Handbook, Analog Devices)

DESIGNER TOOLS

So you have plenty of options when designing a filter. Fortunately, there are great computer-based design tools made for the design engineer. Some are expensive, but plenty are free. In particular, several op-amp suppliers offer filter design tools for their products. I like Analog Devices’s Analog Filter Wizard (www.analog.com/designtools/en/filterwizard/). It’s powerful and doesn’t require a PC installation. Other solutions include Texas Instruments’s Webench Filter Designer, Microchip Technology’s FilterLab, Linear Technology’s FilterCAD, and some others.

FIGURE 8 With a tool like the Analog Filter Wizard (Analog Devices), life is easy

FIGURE 8: With a tool like the Analog Filter Wizard (Analog Devices), life is easy. Click image to enlarge.

As an example, Figure 8 shows a typical session with Analog Devices’s Analog Filter Design. Basically, you start by selecting the filter type (here a low-pass), the required gain in the pass-band, the cutoff frequency, and the attenuation you want at a given stop-band frequency. A slider enables you to browse through several designs—namely, Chebyshev, Butterworth, and others. The next window enables you select the desired tolerance for the capacitors and resistors and actually draw the filter’s full schematic (of course using an op-amp from the supplier who offered the tool). Lastly, the resulting frequency, phase, and time plots are generated, taking into account the tolerance of the parts. Other options enable you to calculate the power consumption of the design or its noise figure. Of course, the beauty of such a tool is that you can try tens of designs in minutes and select the most adequate for your specifications and budget.

WRAPPING UP

Here we are. As always, I have only scratched the subject’s surface. Anyway, I hope you grasped the key concepts. Go through the content listed in the Resources section of this article, and don’t forget to practice on your own. Maybe you should stop reading this magazine now (don’t forget to come back to the issue later), download one of the filter design tools, and play with the settings. It would be the best way to really understand the difference between a fourth-order Butterworth filter and a third-order Chebyshev filter. Have fun and don’t be afraid of filters.

Robert Lacoste lives in France, near Paris. He has 25 years of experience in embedded systems, analog designs, and wireless telecommunications. A prize winner in more than 15 international design contests, in 2003 he started his consulting company, ALCIOM, to share his passion for innovative mixed-signal designs. His book (Robert Lacoste’s The Darker Side) was published by Elsevier/Newnes in 2009.

Find and Eliminate Ground Loops

Everything had been fine with my home entertainment center—comprising a TV, surround-sound amplifier, an AM/FM tuner, a ROKU, and a CD/DVD/BlueRay player—until I connected my desktop PC, which stores many of my music and video files on one of its hard drives. With the PC connected, the speakers put out a low level, annoying, 60-Hz hum—a clear indication of a ground loop. All my audio and video (AV) devices are fairly new, quality, brand-name products equipped with two-prong power cords, so even though the PC has a three-prong plug, there should not be multiple signal returns causing the ground loop. This article describes an approach to eliminating ground loops in analog AV systems.

GROUND LOOPS

By definition, ground loops bring about unwanted currents flowing through two or more signal return paths. Thus induction coils are formed, usually of one turn only. These loops pick up interference signals from the environment. Because every conductor has a finite impedance, a voltage potential—Vi = Ig(R1 + R2)—develops between the two connected signal return points. This voltage is the source of the interference: a hum, hiss noise that high-frequency signals pick up (e.g., a local AM station), and so forth. A simplified example is illustrated in Figure 1.

FIGURE 1: Cause of the ground loop interference.

FIGURE 1: Cause of the ground loop interference.

An audio signal source VS in Figure 1—an audio card inside the PC, for example—is connected to an amplifier via a shielded cable. The shield is grounded at both ends to the chassis of both devices. Three-prong power plugs connect the chassis of both AV components to the house power distribution ground wire. Let’s consider the amplifier ground to be the reference point. (It doesn’t matter which point in the loop we pick.) The loop, comprising the cable shield and the power distribution ground wire, picks up all kinds of signals causing loop current Ig to flow and as a result interference voltage Vi to be generated.

Vi is added to the signal from the audio card. The Ig current induced into the loop comes from many potential sources. It can be induced in the ground wire by the current flowing in the 120-VAC hot and its return neutral wires, acting like a transformer. There can be leakages, induction by magnetic fields, capacitive coupling, or an electromagnetic interference (EMI) induction into the loop. Once Vi is added to the signal it is generally impossible to filter it out.

Much of electrical equipment requires the third power prong for safety. This is connected to the chassis and at the electrical distribution panel to the neutral (white wire) and the local ground—usually a metal stake buried in the earth. The earth ground is there to dissipate lightning strikes but has no effect on the ground loops we are discussing.
The ground wire’s primary purpose is safety plus transient and lightning diversion to ground. Under normal circumstances no current should flow through this wire. Should an internal fault in an appliance connect either the neutral (white) or the hot (black or red) wire to the chassis, the green wire shunts the chassis to the ground. Ground fault interrupters (GFI) compare the current through the hot wire to the return through the neutral. If not identical, the GFI disconnects.

Manufacturers of audio equipment know that grounding sensitive equipment at different places along the ground wire results in multiple returns causing ground loops. These facilitate the interference noise to enter the system. From the perspective of electrical safety, the small currents induced in the ground loop can be ignored. Unfortunately, they are large enough to play havoc with sensitive electronics. The simplest solution to the dilemma is to avoid creating ground loops by not grounding the AV equipment. Thus the two-prong plugs have been used on such equipment. To satisfy the safety requirements, the equipment is designed with double insulation, meaning that even in case of an internal fault, a person cannot come to contact with a live metallic part by touching anywhere on the surface of the equipment.

My PC, like most desktops, has a three-prong plug. Figure 2 shows the arrangement. The PC is grounded through its power cord. Unfortunately, the cable TV (CATV) introduces a second ground connection through its coax connector. I measured the resistance between the coax shield as it entered the house and the house power distribution ground wire. The resistance was 340 mΩ, indicating a hard connection between the coax shield and the house ground, the cause of the ground loop. I was unable to establish where that connection was made, but it wasn’t through the earth.

FIGURE 2: Ground loop in my entertainment system

FIGURE 2: Ground loop in my entertainment system

There can be multiple ground loops around a computer system if you have hard-wired peripherals with three-prong plugs, such as some printers, scanners and so forth. Digital circuits are much less sensitive to ground loops than the analog ones, but it is a good idea to minimize potential loops by connecting all your peripherals, other than wireless, into a single power bar.

Ground loops may also be created when long shielded cables are used to interface the PC and the home theatre box. Two shielded cables needed for stereo represent two signal returns creating a ground loop of their own. And then there are video cables. Another loop. Fortunately, connectors on the back of the PC and AV equipment are very close to each other, which means a minimal potential difference between them at low frequencies. Stereo cables keep the loop small. To minimize all the loops’ areas for interference pick-up, I have bundled the interface cables very close to each other with plastic wire ties. In severe situations re-routing the cables or the use of a metal conduit or wireless interfaces may be needed to kill the interference.

FIXES

Having disconnected the CATV cable from the TV, the hum went away. As well, temporarily replacing the PC with a laptop, which is not grounded, also fixed the problem. So how else can we fix those offending multiple returns?

The obvious answer is to break the loop. I strongly suggest you don’t disconnect the PC from the ground by using a two-prong plug adapter or just cutting the ground prong off. It will render your system unsafe. What you need is a ground isolator. Jensen Transformers, for example, sell isolators such as VRD-IFF or PC-2XR to break the ground connection, but you can build one for a small fraction of the purchase price. Figure 3 and Figure 4 show you how.

FIGURE 3: Ground isolator for CATV coax

FIGURE 3: Ground isolator for CATV coax

To break the ground loop caused by the CATV, you can make a little gizmo shown in Figure 3. J1 and J2 are widely available cable TV female connectors. C1 and C2 capacitors placed between them should be about 0.01 µF each. The assembly does not require a printed circuit board. You might place it in a tiny box or just solder everything together, wrap it with electrical tape, and put it somewhere out of the way. Remember that the capacitors’ working voltage must be at least double the power distribution voltage. That is 250 V in North America and more than 500 V elsewhere in the world.

FIGURE 4: Ground isolator for three-prong powered appliances

FIGURE 4: Ground isolator for three-prong powered appliances

Figure 4 shows how to break ground for appliances, such as a PC, with three-prong plugs. You can build this circuit into a computer or another appliance, but I find it better to build it as an independent break-out box. The diodes provide open loop for signals up to about 1.3 VPP. A hum is usually of a substantially lower amplitude. C1, 0.01 µF, provides bypass for high-frequency EMI to ground. The loop would be closed for voltages higher than 1.3 VPP, such as the ones due to isolation fault of the hot wire to the chassis. For 120 VAC distribution, D1, D2, and C1 should be rated for 250 V at a minimum. In a circuit branch with a 15-A breaker or fuse, the diodes need to be rated for a minimum of 20 A so that the breaker opens up before the diodes blow. If the appliance takes only a fraction of the rated fuse current, say 2 A, you could use 5-A diodes and include an optional fuse rated for 2 A. For countries with 230-VAC power, the components must be rated accordingly.

You can also break the ground loop by using a power isolation transformer between the power line and the PC, or quality signal transformers on the signal lines. The downside of this is that good isolation and signal transformers are costly and not widely available. Equipment powered from wall warts—and especially those with optically coupled inputs and outputs, common today—is inherently ground loop impervious.

TRIAL & ERROR

This article describes an approach to eliminating ground loops in analog AV systems. While you need to understand how ground loops occur, finding them and eliminating their effects may turn out to be a matter of frustrating trial and error.

George Novacek is a professional engineer with a degree in Cybernetics and Closed-Loop Control. Now retired, he was most recently president of a multinational manufacturer for embedded control systems for aerospace applications. George wrote 26 feature articles for Circuit Cellar between 1999 and 2004. Contact him at gnovacek@nexicom.net with “Circuit Cellar” in the subject line.

This article appears in Circuit Cellar 301 August 2015.

Video Decoder with MIPI-CSI2 Output Interface Supports Next-Generation SoCs

Intersil Corp. recently introduced the TW9992 analog video decoder, which features an integrated MIPI-CSI2 output interface that provides compatibility with the newest SoC processors. The decoder’s MIPI-CSI2 interface simplifies design by making it easier to interface with SoCs, while also lowering the system’s EMI profile. The TW9992 decoder takes both single-ended and differential composite video inputs from a vehicle’s backup safety camera, and is the latest addition to Intersil’s video decoder product family for automotive applications.TW9992-intersil

Designed with built-in diagnostics and superior video quality, the TW9992 addresses the biggest challenges faced by automotive video systems. For example, the decoder’s Automatic Contrast Adjustment (ACA) image enhancement feature overcomes a major challenge for backup camera systems by adapting to rapidly changing lighting conditions. ACA is able to automatically boost up or reduce the brightness/contrast of an image for greater visibility and safety.

In addition, vehicle backup cameras typically employ differential twisted pair cables that require designers to use an operational amplifier (op amp) in front of the video decoder to convert the differential signal to single-ended. The TW9992 decoder eliminates the need for an external op amp by supporting direct differential CVBS inputs, thus reducing system cost and board space. The built-in short-to-battery and short-to-ground detection capability on each differential input channel further enhances video performance and automotive system reliability.

Features and specifications:

  • NTSC/PAL 10-bit ADC analog video decoder with 4H adaptive comb filter
  • MIPI-CSI2 output interface
  • Software selectable analog input control allows for combinations of single-ended or differential CVBS
  • Advanced image enhancement features: automatic contrast adjustment, and programmable hue, brightness, saturation, contrast and sharpness
  • Output voltage: 1.8 to 3.3 V with 3.3 V tolerance
  • Low-power consumption: 100-mW typical
  • Integrated short-to-battery and short-to-ground detection tests
  • AEC-Q100 qualified

The automotive-grade TW9992 analog video decoder is available in a 32-pin wettable flank QFN package. It costs $3 in 1,000-piece quantities.

Source: Intersil Corp.

Online Classroom for Analog Design

Texas Instruments recently launched TI Precision Labs, which is a comprehensive online classroom for analog engineers to take on-demand courses. The free, modular curriculum includes more than 30 training experiences and lab videos covering analog amplifier design considerations with online coursework.TI OnlineClassroomAnalog

TI Precision Labs incorporates a variety of tools to bring the online training experience to life. A $199 TI Precision Labs Op Amp Evaluation Module (TI-PLABS-AMP-EVM) enables engineers to complete each demonstrated learning activity along with the trainer. The curriculum also provides access to free design tools, such as TI Designs reference designs and TI’s TINA-TI SPICE model simulator.

Engineers can evaluate circuits and small-signal AC performance created during the trainings with National Instruments’s VirtualBench all-in-one instrument and TI’s Bode Analyzer Software for VirtualBench, as well as standard engineering bench equipment.

Key features and benefits of TI Precision Labs:

  • Experiential learning applies theory to real-world, hands-on examples with lab demonstration videos.
  • A customized learning environment provides recommended training tracks on topics such as noise, bandwidth and input/output swing, while enabling engineers to pick and choose courses based on individual needs and interests.
  • Accelerated learning for recent graduates eases the transition from undergraduate theoretical-based learning to real-world designing.
  • Robust learning materials include a downloadable presentation workbook and lab manual, as well as TI’s Analog Engineer’s Pocket Reference, which puts commonly used board- and system-level formulas at your fingertips.
  • Expert support: A TI Precision Labs support forum is available on the TI E2E Community to answer questions resulting from the training.

The TI Precision Labs training curriculum is free to anyone with a myTI account. In addition to free training, other benefits of myTI registration include the ability to purchase TI integrated circuits (ICs), evaluation modules, development kits and software; request product samples; get technical assistance through the TI E2E Community; create, simulate and optimize systems in the WEBENCH Design Center; and more.
TI Precision Labs curriculum is housed in the new TI Training Center, which connects engineers with the technical training they need to find solutions to their design challenges anytime, anywhere.

In addition to the on-demand courses, in-person, hands-on trainings covering a variety of precision amplifier topics, such as noise, offset, input bias, slew rate and bandwidth, are scheduled for May in Schaumburg, IL and Pewaukee, WI. Both live trainings require registration and cost $99 to attend. More in-person training dates in the United States will be added.

Source: Texas Instruments

New Microcontrollers Feature Advanced Analog & Digital Integration

Microchip Technology recently announced a new family of 8-bit PIC microcontrollers (MCUs) with the PIC16(L)F1769 family, which is the first to offer up to two independent closed-loop channels. This is achieved with the addition of the Programmable Ramp Generator (PRG), which automates slope and ramp compensation, increases stability and efficiencies in hybrid power conversion applications. The PRG provides real-time responses to a system change, without CPU interaction for multiple independent power channels. This allows customers the ability to reduce latency and component counts while improving system efficiency.Microchip PIC16(L)F1769

The PIC16(L)F1769 family includes intelligent analog and digital peripherals, including tristate op-amps, 10-bit ADCs, 5- and 10-bit DACs, 10- and 16-bit PWMs, and high-speed comparators, along with two 100-mA, high-current I/Os. The combination of these integrated peripherals help support the demands of multiple independent closed-loop power channels and system management, while providing an 8-bit platform that simplifies design, enables higher efficiency and increase performance while helping eliminate many discrete components in power-conversion systems.

In addition to power-conversion peripherals, these PIC MCUs have a unique hardware-based LED dimming control function enabled by the interconnections of the Data Signal Modulator (DSM), op amp and 16-bit PWM. The combination of these peripherals creates a LED-dimming engine synchronizing switching control eliminating LED current overshoot and decay. The synchronization of the output switching helps smooth dimming, minimizes color shifting, increases LED life and reduces heat. This family also includes Core Independent Peripherals (CIPs), such as the Configurable Logic Cell (CLC), Complementary Output Generator (COG), and Zero Cross Detect (ZCD). These CIPs take 8-bit PIC MCU performance to a new level, as they are designed to handle tasks with no code or supervision from the CPU to maintain operation, after initial configuration. As a result, they simplify the implementation of complex control systems and give designers the flexibility to innovate. The CLC peripheral allows designers to create custom logic and interconnections specific to their application, reducing interrupt latency, saving code space and adding functionality. The COG peripheral is a powerful waveform generator that can generate complementary waveforms with fine control of key parameters, such as phase, dead-band, blanking, emergency shut-down states, and error-recovery strategies. It provides a cost-effective solution, saving both board space and component cost. The ZCD senses when high voltage AC signal crosses through ground, ideal for TRIAC control functions.

These new 8-bit PIC MCUs provide the capability for multiple independent, closed loop power channels and system management making these products appealing to various power supply, battery management, LED lighting, exterior/interior automotive lighting and general-purpose applications. Along with all these features, the family offers EUSART, I2C/SPI and eXtreme Low Power (XLP) Technology, which are all offered in small form-factor packages, ranging from 14- to 20-pin packages.

The PIC16(L)F1769 family is supported by Microchip’s standard suite of world-class development tools, including the MPLAB ICD 3 (part # DV164035, $199.95) and PICkit 3 (part # PG164130, $47.95) and MPLAB Code Configurator, which is a plug-in for Microchip’s freeMPLAB X IDE provides a graphical method to configure 8-bit systems and peripheral features, and gets you from concept to prototype in minutes by automatically generating efficient and easily modified C code for your application.

The PIC(L)F1764, PIC(L)F1765, PIC16(L)F1768, and PIC(L)F1769 are available now for sampling in 14- and 20-pins in PDIP, SOIC, SSOP, TSSOP, and QFN packages. Pricing for the family starts at $0.87 each, in 10,000-unit quantities.

Source: Microchip Technology

24-Bit Sigma Delta A/D Converter

Analog Devices recently announced a 24-bit sigma-delta A/D converter with a fast and flexible output data rate for high-precision instrumentation and process control applications

The AD7175-2 converter delivers 24 noise-free bits at 20 SPS and 17.2 noise-free bits at 250 ksps providing you with a wider dynamic range. With twice the throughput for the same power consumption versus competing solutions, the AD7175-2 enables faster, more responsive measurement systems providing a 50-ksps/channel scan rate with a 20-µs settling time.Analog-AD7175-2-Product-Release-Image

The integrated, low-noise, true rail-to-rail input buffer enables quick and easy sensor interfacing, reduces design and layout complexity, simplifies analog drive circuitry and reduces PCB area. The AD717x family, with a wide range of pin and software compatible devices, allows consolidation and standardization across system platforms.

According to Analog Devices, the converter gives “designers a wider dynamic range, which enables smaller signal deviations to be measured as required within analytical laboratory instrumentation systems.”

Specs and features:

  • 2x the throughput for the same power consumption in comparison to other devices
  • Enables faster measurement systems providing a 50-ksps/channel scan rate with 20-µs settling time.
  • Integrated true rail-to-rail input buffer for easy sensor interfacing and simplified analog drive circuitry
  • User-configurable input channels
  • 2 differential or 4 single-ended channels
  • Per-channel independent programmability
  • Integrated 2.5-V buffered 2-ppm/°C reference
  • Flexible and per-channel programmable digital filters
  • Enhanced filters for simultaneous 50-Hz and 60-Hz rejection
  • −40°C to +105°C operating temperature range

Source: Analog Devices

The World Is Analog

The world we live in is analog. We are analog. Any inputs we can perceive are analog. For example, sounds are analog signals; they are continuous time and continuous value. Our ears listen to analog signals and we speak with analog signals. Images, pictures, and video are all analog at the source and our eyes are analog sensors. Measuring our heartbeat, tracking our activity, all requires processing analog sensor information.

Computers are digital. Information is represented with discrete time and amplitude quantized signals using digital bits. Such representation lends itself to efficient processing and long-term storage of signals and information. But information and signals come from the physical world and need to move back into the physical world for us to perceive them. No matter how “digital” our electronic devices get, they always require interfaces that translate signals from the physical world into the digital world of electronics.

Even when computers talk to computers, analog interfaces are required. To transmit information over long distances (e.g., over a high-speed bus between the memory and the processor or over a wired network connection), the digital information needs to be moved into an analog format at the transmitter to drive the communication channel. At the receiver, the signals typically picked up from the channel do not look anymore like digital signals and need to be processed in the analog domain before they can be converted back into digital information. This is even more so if we consider wireless communications, where the digital information needs to be modulated on a high-speed radio-frequency (RF) carrier in the transmitter and demodulated at the receiver. RF electronics are also analog in nature.

The semiconductor industry has lived through tremendous advances fueled by what is known as Moore’s law: about every two years, thanks to increasing device miniaturization, the number of devices on a chip doubles. This exponential scaling has led to unprecedented advances in computing and software and has made the digitization of most information possible. Our literature, music, movies, and pictures are all processed and stored in digital format nowadays. Digital chips make up most of the volume of chips fabricated and it is thus economically desirable to fine-tune CMOS technologies for digital circuits. But electronic systems need analog interfaces to connect the bits to the world and most consumer products now rely on System-on-Chip (SoC) solutions where one integrated circuit contains the whole system function, from interfaces to digital signal processing and memory blocks. SoCs need a lot of analog interfaces, but their area is mainly composed of digital blocks (often over 90%). As technology scales, the performance of the digital core improves and this in turn increases the requirements of the analog interfaces.

Today’s analog designers are thus asked to design more interfaces with higher performance but using circuits that are as compatible with digital circuits as possible. This trend emerged a few decades ago and has grown stronger and stronger driven by the continuing increase of the functional density of SoCs. Not only do SoCs need more interfaces and better interfaces, the analog performance of highly miniaturized devices like nanometer CMOS transistors has steadily degraded.
 

This essay appears in Circuit Cellar #292 November 2014. 

 
Making nanoscale transistors is great to increase the functional density, but has its drawbacks when designing analog circuits. Nanoscale transistors can only withstand small supply voltages. For example, circuits designed with the latest CMOS transistors can only work with a supply voltage of up to 1 V or so. Traditionally analog circuits operated from voltages as large as +5 V/–5 V, but steadily their supply voltage was forced to reduce to 5 V, to 3.3 V, to 1.8 V, to 1.2 V and projections for future devices are as low as 0.5 V or even 0.2 V since reducing supply voltages also helps digital designs reduce energy consumption. However, for analog circuits, reducing the supply voltage increases their susceptibility to noise or interference and degrades signal quality. To add to the difficulties, nanoscale transistors also exhibit more mismatches, leading to random offset errors, more flicker (1/f) noise, and have poor gain performance.

But analog designers always like to rise up to a challenge. Research in academic and industrial groups has devised a number of novel analog design techniques to build better analog circuits while relying less and less on the performance of an individual device. In my group, for example, we have developed a set of design techniques to design analog circuits that operate with supplies as low as 0.5 V.

Scaling also offers new avenues for designing analog circuits. In nanoscale processes transistors are not able to handle large voltages, but they can intrinsically switch very fast. That allows us to introduce different signal representations at the transistor level for analog functions. Instead of using the traditional voltages or currents, we can now use time delays to represent analog information. This opens a whole range of opportunities to explore new circuits. Technology scaling is driving a paradigm shift in analog design away from the transistor used as a current source or voltage-controlled current source towards the transistor used as a fast switch even when processing analog information. In fact, analog circuits are being built out of what traditionally are digital blocks like switches or ring oscillators. But with the appropriate signal representation and circuit arrangements, they can process analog information to provide interfaces between the real world and the digital world.

The analog electronics field is going through very exciting times. The digital revolution in electronics has made analog even more necessary. And the future is looking bright. Mobile devices are packed with analog interfaces and a host of analog sensors, whose count increases with each new generation. The Internet of Things is all about massively gathering sensor information in one form of another, under strict power-consumption and cost constraints. All this while the traditional analog design techniques are clearly showing their limitations in the face of aggressive device scaling. This makes for a very challenging but a very interesting time for analog designers with plenty of opportunities to make an impact. Analog is the future!

KingetTTFPeter Kinget is a Professor of Electrical Engineering at Columbia University in New York. He received his engineering and PhD degrees in Electrical Engineering from the Katholieke Universiteit in Leuven (Belgium). His research group focusses on the design of analog and RF integrated circuits in scaled technologies and the novel systems or applications they enable in communications, sensing, and power management. (For more information, visit www.ee.columbia.edu/~kinget.)

 

New Digitally Enhanced Power Analog Controllers

Microchip Technology recently announced its latest Digitally Enhanced Power Analog (DEPA) controllers—the MCP19118 and MCP19119—which offer analog PWM control for DC-DC synchronous buck converters up to 40 V with the configurability of a digital microcontroller. MicrochipMCP19118

Interestingly, the devices bring together 40-V operation and PMBus communication interfaces for power-conversion circuit development with an analog control loop that is programmable in the integrated 8-bit PIC core’s firmware.  According to Microchip in a product release, “this integration and flexibility is ideal for power-conversion applications, such as battery-charging, LED-driving, USB Power Delivery, point-of-load and automotive power supplies.”

As expected, Microchip’s MPLAB X, PICkit 3, PICkit serial analyzer, and MPLAB XC8s support the MCP19118/9 DEPA controllers. The MCP19118 and MCP19119 are now available with prices starting at $2.92 each in 5,000-unit quantities.

 

One Professor and Two Orderly Labs

Professor Wolfgang Matthes has taught microcontroller design, computer architecture, and electronics (both digital and analog) at the University of Applied Sciences in Dortmund, Germany, since 1992. He has developed peripheral subsystems for mainframe computers and conducted research related to special-purpose and universal computer architectures for the past 25 years.

When asked to share a description and images of his workspace with Circuit Cellar, he stressed that there are two labs to consider: the one at the University of Applied Sciences and Arts and the other in his home basement.

Here is what he had to say about the two labs and their equipment:

In both labs, rather conventional equipment is used. My regular duties are essentially concerned  with basic student education and hands-on training. Obviously, one does not need top-notch equipment for such comparatively humble purposes.

Student workplaces in the Dortmund lab are equipped for basic training in analog electronics.

Student workplaces in the Dortmund lab are equipped for basic training in analog electronics.

In adjacent rooms at the Dortmund lab, students pursue their own projects, working with soldering irons, screwdrivers, drills,  and other tools. Hence, these rooms are  occasionally called the blacksmith’s shop. Here two such workplaces are shown.

In adjacent rooms at the Dortmund lab, students pursue their own projects, working with soldering irons, screwdrivers, drills, and other tools. Hence, these rooms are occasionally called “the blacksmith’s shop.” Two such workstations are shown.

Oscilloscopes, function generators, multimeters, and power supplies are of an intermediate price range. I am fond of analog scopes, because they don’t lie. I wonder why neither well-established suppliers nor entrepreneurs see a business opportunity in offering quality analog scopes, something that could be likened to Rolex watches or Leica analog cameras.

The orderly lab at home is shown here.

The orderly lab in Matthes’s home is shown here.

Matthes prefers to build his  projects so that they are mechanically sturdy. So his lab is equipped appropriately.

Matthes prefers to build mechanically sturdy projects. So his lab is appropriately equipped.

Matthes, whose research interests include advanced computer architecture and embedded systems design, pursues a variety of projects in his workspace. He describes some of what goes on in his lab:

The projects comprise microcontroller hardware and software, analog and digital circuitry, and personal computers.

Personal computer projects are concerned with embedded systems, hardware add-ons, interfaces, and equipment for troubleshooting. For writing software, I prefer PowerBASIC. Those compilers generate executables, which run efficiently and show a small footprint. Besides, they allow for directly accessing the Windows API and switching to Assembler coding, if necessary.

Microcontroller software is done in Assembler and, if required, in C or BASIC (BASCOM). As the programming language of the toughest of the tough, Assembler comes second after wire [i.e., the soldering iron].

My research interests are directed at computer architecture, instruction sets, hardware, and interfaces between hardware and software. To pursue appropriate projects, programming at the machine level is mandatory. In student education, introductory courses begin with the basics of computer architecture and machine-level programming. However, Assembler programming is only taught at a level that is deemed necessary to understand the inner workings of the machine and to write small time-critical routines. The more sophisticated application programming is usually done in C.

Real work is shown here at the digital analog computer—bring-up and debugging of the master controller board. Each of the six microcontrollers is connected to a general-purpose human-interface module.

A digital analog computer in Matthes’s home lab works on master controller board bring-up and debugging. Each of the six microcontrollers is connected to a general-purpose human-interface module.

Additional photos of Matthes’s workspace and his embedded electronics and micrcontroller projects are available at his new website.

 

 

 

A Serene Workspace for Board Evaluation and Writing

 Elecronics engineer, entrepreneur, and author Jack Ganssle recently sent us information about his Finksburg, MD, workspace:

I’m in a very rural area and I value the quietness and the view out of the window over my desk. However, there are more farmers than engineers here so there’s not much of a high-tech community! I work out of the house and share an office with my wife, who handles all of my travel and administrative matters. My corner is both lab space and desk. Some of the equipment changes fairly rapidly as vendors send in gear for reviews and evaluation.

ganssle-workspace

Ganssle’s desk is home to ever-changing equipment. His Agilent Technologies MSO-X-3054A mixed-signal oscilloscope is a mainstay.

The centerpiece, though, is my Agilent Technologies MSO-X-3054A mixed-signal oscilloscope. It’s 500 MHz, 4 GSps, and includes four analog channels and 16 digital channels, as well as a waveform generator and protocol analyzer. I capture a lot of oscilloscope traces for articles and talks, and the USB interface sure makes that easy. That’s pretty common on oscilloscopes, now, but being an old-timer I remember struggling with a Polaroid scope camera.

The oscilloscope’s waveform generator has somewhat slow (20-ns) rise time when making pulses, so the little circuit attached to it sharpens this to 700 ps, which is much more useful for my work. The photo shows a Siglent SDS1102CML oscilloscope on the bench that I’m currently evaluating. It’s amazing how much capability gets packed into these inexpensive instruments.

The place is actually packed with oscilloscopes and logic analyzers, but most are tucked away. I don’t know how many of those little USB oscilloscope/logic analyzers vendors have sent for reviews. I’m partial to bench instruments, but do like the fact that the USB instruments are typically quite cheap. Most have so-so analog performance but the digital sampling is generally great.

Only barely visible in the picture, under the bench there’s an oscilloscope from 1946 with a 2” CRT I got on eBay just for fun. It’s a piece of garbage with a very nonlinear timebase, but a lot of fun. The beam is aimed by moving a magnet around! Including the CRT there are only four tubes. Can you imagine making anything with just four transistors today?

The big signal generator is a Hewlett-Packward 8640B, one of the finest ever made with astonishing spectral purity and a 0.5-dB amplitude flatness across 0.5 MHz to 1 GHz. A couple of digital multimeters and a pair of power supplies are visible as well. The KORAD supply has a USB connection and a serviceable, if klunky, PC application that drives it. Sometimes an experiment needs a slowly changing voltage, which the KORAD manages pretty well.

They’re mostly packed away, but I have a ton of evaluation kits and development boards. A Xilinx MicroZed is shown on the bench. It’s is a very cool board that has a pair of Cortex-A9s plus FPGA fabric in a single chip.

I use IDEs and debuggers from, well, everyone: Microchip Technology, IAR Systems, Keil, Segger, you name it. These run on a variety of processors but, along with so many others, more and more I’m using Cortex-M series parts.

My usual lab work is either evaluating boards, products and instruments, or running experiments that turn into articles. It pains me to see so much engineering is done via superstition today. For example, people pick switch contact debounce times based on hearsay or smoke signals or something. Engineers need data, so I tested about 50 pairs of switches to determine what real bounce characteristics are. The results are on my website. Ditto for watchdog timers and other important issues embedded people deal with.

Ganssle notes that his other “bench” is his woodworking shop. To learn more about Ganssle, read our 2013 interview.

A Workspace for Microwave Imaging, Small Radar Systems, and More

Gregory L. Charvat stays very busy as an author, a visiting research scientist at the Massachusetts Institute of Technology (MIT) Media Lab, and the hardware team leader at the Butterfly Network, which brings together experts in computer science, physics, and electrical engineering to create new approaches to medical diagnostic imaging and treatment.

If that wasn’t enough, he also works as a start-up business consultant and pursues personal projects out of the basement-garage workspace of his Westbrook, CT, home (see Photo 1). Recently, he sent Circuit Cellar photos and a description of his lab layout and projects.

Photo 1

Photo 1: Charvat, seated at his workbench, keeps his equipment atop sturdy World War II-era surplus lab tables.

Charvat’s home setup not only provides his ideal working conditions, but also considers  frequent moves required by his work.

Key is lots of table space using WW II surplus lab tables (they built things better back then), lots of lighting, and good power distribution.

I’m involved in start-ups, so my wife and I move a lot. So, we rent houses. When renting, you cannot install the outlets and things needed for a lab like this. For this reason, I built my own line voltage distribution panel; it’s the big thing with red lights in the middle upper left of the photos of the lab space (see Photo 2).  It has 16 outlets, each with its own breaker, pilot lamp (not LED).  The entire thing has a volt and amp meter to monitor power consumption and all power is fed through a large EMI filter.

Photo 2: This is another view of the lab, where strong lighting and two oscilloscopes are the minimum requirements.

Photo 2: This is another view of the lab, where strong lighting and two oscilloscopes are the minimum requirements.

Projects in the basement-area workplace reflect Charvat’s passion for everything from microwave imaging systems and small radar sensor technology to working with vacuum tubes and restoring antique electronics.

My primary focus is the development of microwave imaging systems, including near-field phased array, quasi-optical, and synthetic-aperture radar (SAR). Additionally, I develop small radar sensors as part of these systems or in addition to. Furthermore, I build amateur radio transceivers from scratch. I developed the only all-tube home theater system (published in the May-June 2012 issues of audioXpress magazine) and like to restore antique radio gear, watches, and clocks.

Charvat says he finds efficient, albeit aging, gear for his “fully equipped microwave, analog, and digital lab—just two generations too late.”

We’re fortunate to have access to excellent test gear that is old. I procure all of this gear at ham fests, and maintain and repair it myself. I prefer analog oscilloscopes, analog everything. These instruments work extremely well in the modern era. The key is you have to think before you measure.

Adequate storage is also important in a lab housing many pieces for Charvat’s many interests.

I have over 700 small drawers full of new inventory.  All standard analog parts, transistors, resistors, capacitors of all types, logic, IF cans, various radio parts, RF power transistors, etc., etc.

And it is critical to keep an orderly workbench, so he can move quickly from one project to the next.

No, it cannot be a mess. It must be clean and organized. It can become a mess during a project, but between projects it must be cleaned up and reset. This is the way to go fast.  When you work full time and like to dabble in your “free time” you must have it together, you must be organized, efficient, and fast.

Photos 3–7 below show many of the radar and imaging systems Charvat says he is testing in his lab, including linear rail SAR imaging systems (X and X-band), a near-field S-band phased-array radar, a UWB impulse X-band imaging system, and his “quasi-optical imaging system (with the big parabolic dish).”

Photo 3: This shows impulse rail synthetic aperture radar (SAR) in action, one of many SAR imaging systems developed in Charvat’s basement-garage lab.

Photo 3: This photo shows the impulse rail synthetic aperture radar (SAR) in action, one of many SAR imaging systems developed in Charvat’s basement-garage lab.

Photo 4: Charvat built this S-band, range-gated frequency-modulated continuous-wave (FMCW) rail SAR imaging system

Photo 4: Charvat built this S-band, range-gated frequency-modulated continuous-wave (FMCW) rail SAR imaging system.

Photo 5: Charvat designed an S-band near-field phased-array imaging system that enables through-wall imaging.

Photo 5: Charvat designed an S-band near-field phased-array imaging system that enables through-wall imaging.

Photo 5: Charvat's X-band, range-gated UWB FMCW rail SAR system is shown imaging his bike.

Photo 6: Charvat’s X-band, range-gated UWB FMCW rail SAR system is shown imaging his bike.

Photo 7: Charvat’s quasi-optical imaging system includes a parabolic dish.

Photo 7: Charvat’s quasi-optical imaging system includes a parabolic dish.

To learn more about Charvat and his projects, read this interview published in audioXpress (October 2013). Also, Circuit Cellar recently featured Charvat’s essay examining the promising future of small radar technology. You can also visit Charvat’s project website or follow him on Twitter @MrVacuumTube.

New 8-bit PIC Microcontrollers: Intelligent Analog & Core Independent Peripherals

Microchip Technology, Inc. announced Monday from EE Live! and the Embedded Systems Conference in San Jose the PIC16(L)F170X and PIC16(L)F171X family of 8-bit microcontrollers (MCUs), which combine a rich set of intelligent analog and core independent peripherals, along with cost-effective pricing and eXtreme Low Power (XLP) technology. Available in 14-, 20-, 28-, and 40/44-pin packages, the 11-member PIC16F170X/171X family of microcontrollers integrates two op-amps to drive analog control loops, sensor amplification and basic signal conditioning, while reducing system cost and board space.

PIC16F170X/171X MCUs reduce design complexity and system BOM cost with integrated op-amps, zero cross detect, and peripheral pin select.

PIC16F170X/171X MCUs reduce design complexity and system BOM cost with integrated op-amps, zero cross detect, and peripheral pin select.

These new devices also offer built-in Zero Cross Detect (ZCD) to simplify TRIAC control and minimize the EMI caused by switching transients. Additionally, these are the first PIC16 MCUs with Peripheral Pin Select, a pin-mapping feature that gives designers the flexibility to designate the pinout of many peripheral functions.

The PIC16F170X/171X are general-purpose microcontrollers that are ideal for a broad range of applications, such as consumer (home appliances, power tools, electric razors), portable medical (blood-pressure meters, blood-glucose meters, pedometers), LED lighting, battery charging, power supplies and motor control.

The new microcontrollers feature up to 28 KB of self-read/write flash program memory, up to 2 KB of RAM, a 10-bit ADC, a 5-/8-bit DAC, Capture-Compare PWM modules, stand-alone 10-bit PWM modules and high-speed comparators (60 ns typical response), along with EUSART, I2C and SPI interface peripherals. They also feature XLP technology for typical active and sleep currents of just 35 µA/MHz and 30 nA, respectively, helping to extend battery life and reduce standby current consumption.

The PIC16F170X/171X family is supported by Microchip’s standard suite of world-class development tools, including the PICkit 3 (part # PG164130, $44.95), MPLAB ICD 3 (part # DV164035, $189.99), PICkit 3 Low Pin Count Demo Board (part # DM164130-9, $25.99), PICDEM Lab Development Kit (part # DM163045, $134.99) and PICDEM 2 Plus (part # DM163022-1, $99.99). The MPLAB Code Configurator is a free tool that generates seamless, easy-to-understand C code that is inserted into your project. It currently supports the PIC16F1704/08, and is expected to support the PIC16F1713/16 in April, along with all remaining microcontrollers in this family soon thereafter.

The PIC16(L)F1703/1704/1705 microcontrollers are available now for sampling and production in 14-pin PDIP, TSSOP, SOIC and QFN (4 x 4 x 0.9 mm) packages. The PIC16F1707/1708/1709 microcontrollers are available now for sampling and production in 20-pin PDIP, SSOP, SOIC and QFN (4 x 4 x 0.9 mm) packages. The PIC16F1713/16 MCUs are available now for sampling and production in 28-pin PDIP, SSOP, SOIC, QFN (6 x 6 x 0.9 mm) and UQFN (4 x 4 x 0.5 mm) packages. The PIC16F1718 microcontrollers are expected to be available for sampling and production in May 2014, in 28-pin PDIP, SSOP, SOIC, QFN (6 x 6 x 0.9 mm) and UQFN (4 x 4 x 0.5 mm) packages. The PIC16F1717/19 microcontrollers are expected to be available for sampling and production in May 2014, in 40/44-pin PDIP, TQFP and UQFN (5 x 5 x 0.5 mm). Pricing starts at $0.59 each, in 10,000-unit quantities.

Source: Microchip Technology, Inc.

Client Profile: Integrated Knowledge Systems

Integrated Knowledge Systems' NavRanger board

Integrated Knowledge Systems’ NavRanger board

Phoenix, AZ

CONTACT: James Donald, james@iknowsystems.com
www.iknowsystems.com

EMBEDDED PRODUCTS: Integrated Knowledge Systems provides hardware and software solutions for autonomous systems.
featured Product: The NavRanger-OEM is a single-board high-speed laser ranging system with a nine-axis inertial measurement unit for robotic and scanning applications. The system provides 20,000 distance samples per second with a 1-cm resolution and a range of more than 30 m in sunlight when using optics. The NavRanger also includes sufficient serial, analog, and digital I/O for stand-alone robotic or scanning applications.

The NavRanger uses USB, CAN, RS-232, analog, or wireless interfaces for operation with a host computer. Integrated Knowledge Systems can work with you to provide software, optics, and scanning mechanisms to fit your application. Example software and reference designs are available on the company’s website.

EXCLUSIVE OFFER: Enter the code CIRCUIT2014 in the “Special Instructions to Seller” box at checkout and Integrated Knowledge Systems will take $20 off your first order.


 

Circuit Cellar prides itself on presenting readers with information about innovative companies, organizations, products, and services relating to embedded technologies. This space is where Circuit Cellar enables clients to present readers useful information, special deals, and more.

Build an Inexpensive Wireless Water Alarm

The best DIY electrical engineering projects are effective, simple, and inexpensive. Devlin Gualtieri’s design of a wireless water alarm, which he describes in Circuit Cellar’s February issue, meets all those requirements.

Like most homeowners, Gualtieri has discovered water leaks in his northern New Jersey home after the damage has already started.

“In all cases, an early warning about water on the floor would have prevented a lot of the resulting damage,” he says.

You can certainly buy water alarm systems that will alert you to everything from a leak in a well-water storage tank to moisture from a cracked boiler. But they typically work with proprietary and expensive home-alarm systems that also charge a monthly “monitoring” fee.

“As an advocate of free and open-source software, it’s not surprising that I object to such schemes,” Gualtieri says.

In February’s Circuit Cellar magazine, now available for membership download or single-issue purchase, Gualtieri describes his battery-operated water alarm. The system, which includes a number of wireless units that signal a single receiver, includes a wireless receiver, audible alarm, and battery monitor to indicate low power.

Photo 1: An interdigital water detection sensor is shown. Alternate rows are lengths of AWG 22 copper wire, which is either bare or has its insulation removed. The sensor is shown mounted to the bottom of the box containing the water alarm circuitry. I attached it with double-stick foam tape, but silicone adhesive should also work.

Photo 1: An interdigital water detection sensor is shown. Alternate rows are lengths of AWG 22 copper wire, which is either bare or has its insulation removed. The sensor is shown mounted to the bottom of the box containing the water alarm circuitry. I attached it with double-stick foam tape, but silicone adhesive should also work.

Because water conducts electricity, Gualtieri sensors are DIY interdigital electrodes that can lie flat on a surface to detect the first presence of water. And their design couldn’t be easier.

“You can simply wind two parallel coils of 22 AWG wire on a perforated board about 2″ by 4”, he says. (See Photo 1.)

He also shares a number of design “tricks,” including one he used to make his low-battery alert work:

“A battery monitor is an important feature of any battery-powered alarm circuit. The Microchip Technology PIC12F675 microcontroller I used in my alarm circuit has 10-bit ADCs that can be optionally assigned to the I/O pins. However, the problem is that the reference voltage for this conversion comes from the battery itself. As the battery drains from 100% downward, so does the voltage reference, so no voltage change would be registered.

Figure 1: This is the portion of the water alarm circuit used for the battery monitor. The series diodes offer a 1.33-V total  drop, which offers a reference voltage so the ADC can see changes in the battery voltage.

Figure 1: This is the portion of the water alarm circuit used for the battery monitor. The series diodes offer a 1.33-V total drop, which offers a reference voltage so the ADC can see changes in the battery voltage.

“I used a simple mathematical trick to enable battery monitoring. Figure 1 shows a portion of the schematic diagram. As you can see, the analog input pin connects to an output pin, which is at the battery voltage when it’s high through a series connection of four small signal diodes (1N4148). The 1-MΩ resistor in series with the diodes limits their current to a few microamps when the output pin is energized. At such low current, the voltage drop across each diode is about 0.35 V. An actual measurement showed the total voltage drop across the four diodes to be 1.33 V.

“This voltage actually presents a new reference value for my analog conversion. The analog conversion now provides the following digital values:

EQ1Table 1 shows the digital values as a function of battery voltage. The nominal voltage of three alkaline cells is 4.75 V. The nominal voltage of three lithium cells is 5.4 V. The PIC12F675 functions from approximately 2 to 6.5 V, but the wireless transmitter needs as much voltage as possible to generate a reliable signal. I arbitrarily coded the battery alarm at 685, or a little above 4 V. That way, there’s still enough power to energize the wireless transmitter at a useful power level.”

Table 1
Battery Voltage ADC Value
5 751
4.75 737
4.5 721
4.24 704
4 683
3.75 661

 

Gaultieri’s wireless transmitter, utilizing lower-frequency bands, is also straightforward.

Photo 2 shows one of the transmitter modules I used in my system,” he says. “The round device is a surface acoustic wave (SAW) resonator. It just takes a few components to transform this into a low-power transmitter operable over a wide supply voltage range, up to 12 V. The companion receiver module is also shown. My alarm has a 916.5-MHz operating frequency, but 433 MHz is a more popular alarm frequency with many similar modules.”

These transmitter and receiver modules are used in the water alarm. The modules operate at 916.5 MHz, but 433 MHz is a more common alarm frequency with similar modules. The scale is inches.

Photo 2: These transmitter and receiver modules are used in the water alarm. The modules operate at 916.5 MHz, but 433 MHz is a more common alarm frequency with similar modules. The scale is inches.

Gualtieri goes on to describe the alarm circuitry (see Photo 3) and receiver circuit (see Photo 4.)

For more details on this easy and affordable early-warning water alarm, check out the February issue.

Photo 3: This is the water alarm’s interior. The transmitter module with its antenna can be seen in the upper right. The battery holder was harvested from a $1 LED flashlight. The box is 2.25“ × 3.5“, excluding the tabs.

Photo 3: This is the water alarm’s interior. The transmitter module with its antenna can be seen in the upper right. The battery holder was harvested from a $1 LED flashlight. The box is 2.25“ × 3.5“, excluding the tabs.

Photo 4: Here is my receiver circuit. One connector was used to monitor the signal strength voltage during development. The other connector feeds an input on a home alarm system. The short antenna reveals its 916.5-MHz operating frequency. Modules with a 433-MHz frequency will have a longer antenna.

Photo 4: Here is my receiver circuit. One connector was used to monitor the signal strength voltage during development. The other connector feeds an input on a home alarm system. The short antenna reveals its 916.5-MHz operating frequency. Modules with a 433-MHz frequency will have a longer antenna.